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general description the MAX17067 boost converter incorporates high- performance (at 1.2mhz), current-mode, fixed-frequency, pulse-width modulation (pwm) circuitry with a built-in 0.15 n-channel mosfet to provide a highly efficient regulator with fast response. high switching frequency (640khz or 1.2mhz selectable) allows for easy filtering and faster loop performance. an external compensation pin provides the user flexibility in determining loop dynamics, allowing the use of small, low equivalent-series-resistance (esr) ceramic output capacitors. the device can produce an output voltage as high as 18v. soft-start is programmed with an external capacitor, which sets the input-current ramp rate. the MAX17067 is avail- able in a space-saving 8-pin max ? package. the ultra- small package and high switching frequency allow the total solution to be less than 1.1mm high. application lcd displays features 90% efficiency adjustable output from v in to 18v 2.4a, 0.15 , 22v power mosfet +2.6v to +4.0v input range pin-selectable 640khz or 1.2mhz switching frequency programmable soft-start small 8-pin ?ax package integrated input voltage clamp circuit MAX17067 low-noise step-up dc-dc converter ________________________________________________________________ maxim integrated products 1 in lx gnd 1 2 3 4 8 7 6 5 ss freq fb comp max top view MAX17067 shdn lx in v in 2.6v to 4v gnd freq v out comp shdn fb MAX17067 on/off ss typical operating circuit 19-3106; rev 0; 1/08 pin configuration ordering information for pricing, delivery, and ordering information, please contact maxim direct at 1-888-629-4642, or visit maxim? website at www.maxim-ic.com. evaluation kit available part temp range pin- package pkg code MAX17067eua+ -40c to +85c 8 max u8+1 max is a registered trademark of maxim integrated products, inc. + denotes a lead-free package.
MAX17067 low-noise step-up dc-dc converter 2 _______________________________________________________________________________________ absolute maximum ratings electrical characteristics (v in = shdn = 3v, freq = 3v, t a = 0? to +85? , unless otherwise noted. typical values are at t a = +25c.) (note 2) stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. these are stress rating s only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specificatio ns is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. lx to gnd ..............................................................-0.3v to +22v shdn , freq to gnd ............................................-0.3v to +7.5v in to gnd (note 1) ...................................................-0.3v to +6v ss, comp, fb to gnd ................................-0.3v to (v in + 0.3v) rms lx pin current ..............................................................1.2a continuous power dissipation (t a = +70c) 8-pin max (derate 4.1mw/c above +70c) ............330mw operating temperature range ...........................-40c to +85c junction temperature ......................................................+150c storage temperature range .............................-65c to +150c lead temperature (soldering, 10s) .................................+300c parameter symbol conditions min typ max units input supply range v in v out < 18v 2.6 4.0 v output voltage 18 v input supply clamp voltage use external limiting resistor; r in = 100 , v in = 10v (note 3) 6.05 6.40 6.60 v v in undervoltage lockout uvlo v in rising, typical hysteresis is 50mv, lx remains off below this level 2.30 2.45 2.57 v v fb = 1.3v, not switching 0.3 0.6 quiescent current i in v fb = 1.0v, switching 1.5 2.5 ma shdn = gnd, t a = +25c 30 60 shutdown supply current i in shdn = gnd, t a = +85c 30 a error amplifier feedback voltage v fb level to produce v comp = 1.24v 1.23 1.24 1.25 v fb input bias current i fb v fb = 1.24v 50 125 200 na feedback-voltage line regulation level to produce v comp = 1.24v, 2.6v < v in < 5.5v 0.05 0.15 %/v transconductance g m i = 5a 100 240 440 s voltage gain a v 3800 v/v oscillator freq = gnd 500 640 780 frequency f osc freq = in 1000 1200 1400 khz maximum duty cycle dc freq = gnd, freq = in 89 92 95 % n-channel switch current limit i lim v fb = 1v, duty cycle = 68% (note 4) 1.8 2.4 3.4 a on-resistance r on 150 275 m leakage current i lxoff v lx = 20v 10 20 a current-sense transresistance r cs 0.2 0.3 0.4 v/a soft-start reset switch resistance 100 charge current v ss = 1.2v 2.5 4.5 6.5 a
MAX17067 low-noise step-up dc-dc converter _______________________________________________________________________________________ 3 electrical characteristics (v in = shdn = 3v, freq = 3v, t a = -40? to +85? , unless otherwise noted.) (note 2) electrical characteristics (continued) (v in = shdn = 3v, freq = 3v, t a = 0? to +85? , unless otherwise noted. typical values are at t a = +25c.) (note 2) parameter symbol conditions min typ max units control inputs input low voltage v il shdn , freq, v in = 2.6v to 4.0v 0.3 x v in v input high voltage v ih shdn , freq, v in = 2.6v to 4.0v 0.7 x v in v hysteresis shdn , freq 0.1 x v in v freq pulldown current i freq 3 6 9 a shdn = gnd, t a = +25c -1 +1 shdn input current i shdn shdn = gnd, t a = +85c 0 a temperature rising 160 thermal shutdown hysteresis 20 c parameter symbol conditions min typ max units input supply range v in v out < 18v 2.6 4.0 v output voltage range 18 v input supply clamp voltage use external limiting resistor; r in = 100 , v in = 10v (note 3) 6.03 6.60 v v in undervoltage lockout uvlo v in rising, typical hysteresis is 80mv, lx remains off below this level 2.30 2.57 v v fb = 1.3v, not switching 0.6 quiescent current i in v fb = 1.0v, switching 2.5 ma error amplifier feedback voltage v fb level to produce v comp = 1.24v 1.227 1.253 v fb input bias current i fb v fb = 1.24v 200 na feedback-voltage line regulation level to produce v comp = 1.24v, 2.6v < v in < 4.0v 0.15 %/v transconductance g m i = 5a 100 440 s oscillator freq = gnd 450 830 frequency f osc freq = in 950 1500 khz maximum duty cycle dc freq = gnd, freq = v in 89 95 %
typical operating characteristics (circuit of figure 1, v in = 3.3v, f osc = 640khz, t a = +25c, unless otherwise noted.) MAX17067 low-noise step-up dc-dc converter 4 _______________________________________________________________________________________ electrical characteristics (continued) (v in = shdn = 3v, freq = 3v, t a = -40? to +85? , unless otherwise noted.) (note 1) parameter symbol conditions min typ max units n-channel switch current limit i lim v fb = 1v, duty cycle = 68% (note 4) 1.8 3.4 a on-resistance r on v in = 3v 275 current-sense transresistance r cs 0.19 0.40 v/a soft-start reset switch resistance 100 charge current v ss = 1.2v 2.5 6.5 a control inputs input low voltage v il shdn , freq, v in = 2.6v to 4.0 v 0.3 x v in v input high voltage v ih shdn , freq, v in = 2.6v to 4.0v 0.7 x v in v note 1: limit on in absolute maximum ratings is for operation without the use of an external resistor for the internal clamp circuit. see the in supply clamp circuit section for in voltage limits during clamping circuit operation. note 2: limits are 100% production tested at t a = +25c. maximum and minimum limits over temperature are guaranteed by design and characterization. note 3: see the in supply clamp circuit section to properly size the external resistor. note 4: current limit varies with duty-cycle slope compensation. see the output-current capability section. MAX17067 toc01 50 1 1000 100 10 efficiency vs. l0ad current (v in = 3.3v, v out = 9v) 70 90 80 100 60 load current (ma) efficiency (%) f osc = 1.2mhz l = 3.3 h f osc = 640khz l = 4.7 h -0.5 1 1000 100 10 step-up converter load regulation 0 1.0 0.5 MAX17067 toc02 load current (ma) regulation (%) l = 3.3 h input voltage (v) 500 2.5 5.5 4.5 3.5 5.0 4.0 3.0 switching frequency vs. input voltage 800 600 1200 1000 1400 900 700 1300 1100 MAX17067 toc03 switching frequency (khz) freq = in freq = gnd
MAX17067 low-noise step-up dc-dc converter _______________________________________________________________________________________ 5 0 0.5 2.5 2.0 1.5 1.0 3.5 3.0 4.0 2.5 2.9 3.1 3.3 2.7 3.5 3.7 3.9 supply current vs. supply voltage MAX17067 toc04 supply voltage (v) supply current (ma) nonswitching switching 0v 0a v out 5v/div inductor current 1a/div soft-start (r load = 18 ) MAX17067 toc05 2ms/div load-transient response (i load = 10ma to 200ma) MAX17067 toc06 100 s/div l = 3.3 h r comp = 39k c comp1 = 620pf i out 200ma/div 10ma v out 500ma/div ac-coupled 0v inductor current 500ma/div 0a i out 1a/div 0.1a 9v 0v 0a inductor current 1a/div v out 200mv/div ac-coupled 10 s/div pulsed load-transient response (i load = 40ma to 1.1a) MAX17067 toc07 l = 3.3 h r comp = 39k c comp1 = 620pf typical operating characteristics (continued) (circuit of figure 1, v in = 3.3v, f osc = 640khz, t a = +25c, unless otherwise noted.) lx 5v/div inductor current 1a/div 0v 0a 1 s/div switching waveforms (i load = 500ma) MAX17067 toc08
MAX17067 low-noise step-up dc-dc converter 6 _______________________________________________________________________________________ pin description switch pin. connect the inductor/catch diode to lx and minimize the trace area for lowest emi. lx 5 supply pin. bypass in with at least a 1f ceramic capacitor directly to gnd. in 6 frequency select input. when freq is low, the oscillator frequency is set to 640khz. when freq is high, the frequency is 1.2mhz. this input has a 5a pulldown current. freq 7 soft-start control pin. connect a soft-start capacitor (c ss ) to this pin. leave open for no soft-start. the soft- start capacitor is charged with a constant current of 4a. full current limit is reached after t = 2.5 x 10 5 c ss . the soft-start capacitor is discharged to ground when shdn is low. when shdn goes high, the soft-start capacitor is charged to 0.5v, after which soft-start begins. ss 8 ground gnd 4 active-low shutdown control input. drive shdn low to turn off the MAX17067. shdn 3 pin feedback pin. reference voltage is 1.24v nominal. connect an external resistor-divider tap to fb and minimize the trace area. set v out according to: v out = 1.24v (1 + r1 / r2). see figure 1. fb 2 compensation pin for error amplifier. connect a series rc from comp to ground. see the loop compensation section for component selection guidelines. comp 1 function name detailed description the MAX17067 is a highly efficient power supply that employs a current-mode, fixed-frequency pwm architec- ture for fast-transient response and low-noise operation. the device regulates the output voltage through a com- bination of an error amplifier, two comparators, and sev- eral signal generators (figure 2). the error amplifier compares the signal at fb to 1.24v and varies the comp output. the voltage at comp determines the cur- rent trip point each time the internal mosfet turns on. as the load varies, the error amplifier sources or sinks current to the comp output accordingly to produce the inductor peak current necessary to service the load. to maintain stability at high duty cycle, a slope-compensa- tion signal is summed with the current-sense signal. at light loads, this architecture allows the ics to skip cycles to prevent overcharging the output voltage. in this region of operation, the inductor ramps up to a fixed peak value, discharges to the output, and waits until another pulse is needed again. lx in v in 2.6v to 4.0v gnd freq v out comp ss shdn fb r1 r2 l 0.027 f MAX17067 c out c1 10 f 6.3v r comp c comp c comp2 d1 mbrs130lt1 c in 640khz 1.2mhz on/off v in figure 1. typical application circuit
MAX17067 low-noise step-up dc-dc converter _______________________________________________________________________________________ 7 in supply clamp circuit the MAX17067 features an internal clamp to allow appli- cations where there is overvoltage stress on the supply line. in many cases, high-voltage spikes happen on pro- duction lines and are difficult to protect against. the MAX17067s internal clamp circuit can solve this prob- lem. the internal clamp circuit limits the voltage at the in pin to 6.4v (typ) to protect the in pin from a continuous or transient overvoltage stress condition on the supply line. to use the clamp circuit, put a series resistor (r in ) between supply and in, and a decoupling capacitor (1f typical) from in to gnd. to properly size the exter- nal resistor, several factors should be considered: ? the maximum current for the clamp is 40ma, and the clamp voltage at the in pin is 6.05v (min). therefore, the external resistor is: ? power dissipation in the clamp is in addition to the total power loss. ? the external resistor causes a dc voltage drop in the in supply line. the voltage at the in pin has to be properly maintained when clamping is used. the worst-case quiescent current of the in pin is 2.5ma; therefore, the worst-case voltage drop is 2.5ma multiplied by r in . output-current capability the output-current capability of the MAX17067 is a function of current limit, input voltage, operating fre- quency, and inductor value. because of the slope com- pensation used to stabilize the feedback loop, the duty cycle affects the current limit. the output-current capa- bility is governed by the following equation: i out(max) = [i lim x (1.26 - 0.4 x duty) - 0.5 x duty x v in /(f osc x l)] x x v in /v out where: i lim = current limit specified at 68% (see the electrical characteristics ): duty = duty cycle = (v out - v in + v diode )/ (v out - i lim x r on + v diode ) v diode = catch diode forward voltage at i lim = conversion efficiency, 85% nominal rv in in () ? ? ? ? -605 004 .. gnd lx in freq fb comp 4 a 5 a n error comparator error amplifier skip comparator ss clock skip bias shdn MAX17067 current sense control and driver logic soft- start slope compen- sation oscillator 1.24v figure 2. functional diagram
MAX17067 MAX17067 low-noise step-up dc-dc converter 8 _______________________________________________________________________________________ soft-start the MAX17067 can be programmed for soft-start upon power-up with an external capacitor. when the shut- down pin is taken high, the soft-start capacitor (c ss ) is immediately charged to 0.5v. then the capacitor is charged at a constant current of 4.5a (typ). during this time, the ss voltage directly controls the peak inductor current, allowing 0a at v ss = 0.5v to the full current limit at v ss = 1.5v. the maximum load current is available after the soft-start cycle is completed. when the shutdown pin is taken low, the soft-start capacitor is discharged to ground. frequency selection the MAX17067s frequency can be user selected to oper- ate at either 640khz or 1.2mhz. connect freq to gnd for 640khz operation. for a 1.2mhz switching frequen- cy, connect freq to in. this allows the use of small, minimum-height external components while maintaining low output noise. freq has an internal pulldown, allow- ing the user the option of leaving freq unconnected for 640khz operation. shutdown the MAX17067 is shut down to reduce the supply cur- rent to 30a when shdn is low. in this mode, the inter- nal reference, error amplifier, comparators, and biasing circuitry turn off while the n-channel mosfet is turned off. the boost converters output is connected to in by the external inductor and catch diode. thermal-overload protection thermal-overload protection prevents excessive power dissipation from overheating the MAX17067. when the junction temperature exceeds t j = +160 c, a thermal sensor immediately activates the fault protection, which shuts down the MAX17067, allowing the device to cool down. once the device cools down by approximately 20 c, it returns to normal operation. applications information boost dc-dc converters using the MAX17067 can be designed by performing simple calculations for a first iteration. all designs should be prototyped and tested prior to production. table 1 provides a list of compo- nents for a range of standard applications. table 2 lists component suppliers. external component value choice is primarily dictated by the output voltage and the maximum load current, as well as maximum and minimum input voltages. begin by selecting an inductor value. once l is known, choose the diode and capacitors. inductor selection the minimum inductance value, peak current rating, and series resistance are factors to consider when selecting the inductor. these factors influence the converters effi- ciency, maximum output load capability, transient- response time, and output voltage ripple. physical size and cost are also important factors to be considered. table 2. component suppliers 847-639-6400 561-241-7876 847-956-0666 phone 847-639-1469 coilcraft 561-241-9339 coiltronics 847-956-0702 sumida usa fax supplier 803-946-0690 408-986-0424 619-661-6835 847-297-0070 803-626-3123 avx 408-986-1442 kemet 619-661-1055 sanyo 847-699-1194 toko 408-573-4150 408-573-4159 taiyo yuden inductors capacitors phone fax supplier 516-435-1110 310-322-3331 516-543-7100 602-303-5454 847-843-7500 516-864-7630 zetex 847-843-2798 nihon 516-435-1824 central semiconductor 310-322-3332 international rectifier 602-994-6430 motorola diodes table 1. component selection v in (v) v out (v) f osc (hz) l (h) c out (f) r comp (k ) c comp (pf) c comp2 (pf) i out(max) (ma) 3.3 9 1.2m 3.3 10 121 620 10 250 3.3 9 640k 4.7 10 82 1000 10 250
MAX17067 low-noise step-up dc-dc converter _______________________________________________________________________________________ 9 the maximum output current, input voltage, output volt- age, and switching frequency determine the inductor value. very high inductance values minimize the cur- rent ripple and therefore reduce the peak current, which decreases core losses in the inductor and i 2 r losses in the entire power path. however, large induc- tor values also require more energy storage and more turns of wire, which increase physical size and can increase i 2 r losses in the inductor. low inductance val- ues decrease the physical size but increase the current ripple and peak current. finding the best inductor involves choosing the best compromise between circuit efficiency, inductor size, and cost. the equations used here include a constant lir, which is the ratio of the inductor peak-to-peak ripple current to the average dc inductor current at the full load current. the best trade-off between inductor size and circuit efficiency for step-up regulators generally has an lir between 0.3 and 0.5. however, depending on the ac characteristics of the inductor core material and the ratio of inductor resistance to other power path resis- tances, the best lir can shift up or down. if the induc- tor resistance is relatively high, more ripple can be accepted to reduce the number of turns required and increase the wire diameter. if the inductor resistance is relatively low, increasing inductance to lower the peak current can decrease losses throughout the power path. if extremely thin high-resistance inductors are used, as is common for lcd-panel applications, the best lir can increase to between 0.5 and 1.0. once a physical inductor is chosen, higher and lower values of the inductor should be evaluated for efficiency improvements in typical operating regions. calculate the approximate inductor value using the typ- ical input voltage (v in ), the maximum output current (i main(max) ), the expected efficiency ( typ ) taken from an appropriate curve in the typical operating characteristics , and an estimate of lir based on the above discussion: choose an available inductor value from an appropriate inductor family. calculate the maximum dc input cur- rent at the minimum input voltage v in(min) using con- servation of energy and the expected efficiency at that operating point ( min ) taken from an appropriate curve in the typical operating characteristics : calculate the ripple current at that operating point and the peak current required for the inductor: the inductors saturation current rating and the MAX17067s lx current limit (i lim ) should exceed i peak and the inductors dc current rating should exceed i in(dc,max) . for good efficiency, choose an inductor with less than 0.1 series resistance. considering the application circuit in figure 4, the maxi- mum load current (i main(max) ) is 250ma with a 9v output and a typical input voltage of 3.3v. choosing an lir of 0.7 and estimating efficiency of 85% at this operating point: using the applications minimum input voltage (3v) and estimating efficiency of 80% at that operating point: the ripple current and the peak current are: ia a a peak =+ 094 051 2 119 . . . i vvv hv mhz a ripple = ? 393 33 9 12 051 () .. . i av v a in dc max (, ) . . . = 025 9 308 094 l v v vv amhz = ? ? ? ? ? ? ? ? ? ? ? ? ? 33 9 933 025 12 08 2 .. .. . 55 07 33 . . ? ? ? ? ? ? ? h ii i peak in dc max ripple =+ (, ) 2 i vvv lv f ripple in min main in min main osc = ? () () () i iv v in dc max main max main in min min (, ) () () = l v v vv i f lir in main main in main max osc typ = ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? 2 ()
MAX17067 low-noise step-up dc-dc converter 10 ______________________________________________________________________________________ diode selection the output diode should be rated to handle the output voltage and the peak switch current. make sure that the diodes peak current rating is at least i pk and that its breakdown voltage exceeds v out . schottky diodes are recommended. input and output capacitor selection low-esr capacitors are recommended for input bypassing and output filtering. low-esr tantalum capacitors are a good compromise between cost and performance. ceramic capacitors are also a good choice. avoid standard aluminum electrolytic capaci- tors. a simple equation to estimate input and output- capacitor values for a given voltage ripple is as follows: where v ripple is the peak-to-peak ripple voltage on the capacitor. output voltage the MAX17067 operates with an adjustable output from v in to 20v. connect a resistor voltage-divider to fb (see the typical operating circuit ) from the output to gnd. select the resistor values as follows: where v fb , the boost-regulator feedback set point, is 1.24v. since the input bias current into fb is typically zero, r2 can have a value up to 100k without sacrificing accuracy. connect the resistor-divider as close to the ic as possible. loop compensation the voltage feedback loop needs proper compensation to prevent excessive output ripple and poor efficiency caused by instability. this is done by connecting a resis- tor (r comp ) and capacitor (c comp ) in series from comp to gnd, and another capacitor (c comp2 ) from comp to gnd. r comp is chosen to set the high-fre- quency integrator gain for fast-transient response, while c comp is chosen to set the integrator zero to maintain loop stability. the second capacitor, c comp2 , is chosen to cancel the zero introduced by output-capacitance esr. for optimal performance, choose the components using the following equations: r comp = (274 /a 2 x v in x v out x c out /(l x i out ) c comp ? (0.36 x 10 -3 a/ ) x l/v in c comp2 ? (0.0036 a/ ) x r esr x l x i out /(v in x v out ) for the ceramic output capacitor, where esr is small, c comp2 is optional. table 1 shows experimentally verified external component values for several applications. the best gauge of correct loop compensation is by inspecting the transient response of the MAX17067. adjust r comp and c comp as necessary to obtain opti- mal transient performance. soft-start capacitor the soft-start capacitor should be large enough that it does not reach final value before the output has reached regulation. calculate c ss to be: where: c out = total output capacitance including any bypass capacitor on the output bus v out = maximum output voltage i inrush = peak inrush current allowed i out = maximum output current during power-up stage v in = minimum input voltage the load must wait for the soft-start cycle to finish before drawing a significant amount of load current. the duration after which the load can begin to draw maximum load current is: t max = 2.5 x 10 5 c ss c 21 10 c v v v v i i v ss 6 out in out in inrush out out out 2 > ? ? ? ? ? ? ? ? ? rr v v out fb 12 1 =? ? ? ? ? ? ? c 0.5 l i v v pk 2 ripple out ? ? ? ?
MAX17067 low-noise step-up dc-dc converter ______________________________________________________________________________________ 11 application circuits 1-cell to 3.3v sepic power supply figure 3 shows the MAX17067 in a single-ended primary inductance converter (sepic) topology. this topology is useful when the input voltage can be either higher or lower than the output voltage, such as when converting a single lithium-ion (li+) cell to a 3.3v output. l1a and l1b are two windings on a single inductor. the coupling capacitor between these two windings must be a low- esr type to achieve maximum efficiency, and must also be able to handle high ripple currents. ceramic capaci- tors are best for this application. the circuit in figure 3 provides 400ma output current at 3.3v output when operating with an input voltage from +2.6v to +4.0v. amlcd application figure 4 shows a power supply for active matrix (tft- lcd) flat-panel displays. output-voltage transient per- formance is a function of the load characteristic. add or remove output capacitance (and recalculate compen- sation-network component values) as necessary to meet transient performance. regulation performance for secondary outputs (vgoff and vgon) depends on the load characteristics of all three outputs. lx fb c6 open c15 27nf r2 44.2k r1 274k freq in v in 2.6v to 4.0v v out +9v/250ma comp shdn ss d1 gnd u1 MAX17067 c5 620pf r5 121k c1 10 f 10v r3 10 c4 1 f r6 100k l1 3.3 h 6 4 5 2 1 3 7 8 c14 4.7 f c13 1 f c12 1 f d4 d2 1 3 2 2 1 c9 0.1 f c11 0.1 f vgoff -9v vgon +27v 3 c7 10 f 25v d3 2 1 c10 0.1 f 3 figure 4. multiple-output, low-profile (1.2mm max) tft-lcd power supply lx in v in 2.6v to 4.0v gnd l1 = ctx8-1p c out = tpsd226025r0200 c2 10 f freq v out 3.3v cc ss shdn fb d1 r1 1m r2 605k l1a 5.3 h 0.027 f MAX17067 c out 22 f 20v c1 10 f 10v r comp c comp c comp2 l1b 5.3 h figure 3. MAX17067 in a sepic configuration
MAX17067 layout procedure good pcb layout and routing are required in high-fre- quency switching power supplies to achieve good regu- lation, high efficiency, and stability. it is strongly recommended that the evaluation kit pcb layouts be fol- lowed as closely as possible. place power components as close together as possible, keeping their traces short, direct, and wide. avoid interconnecting the ground pins of the power components using vias through an internal ground plane. instead, keep the power components close together and route them in a star ground configura- tion using component-side copper, then connect the star ground to internal ground using multiple vias. low-noise step-up dc-dc converter 12 ______________________________________________________________________________________ chip information transistor count: 3657
MAX17067 low-noise step-up dc-dc converter MAX17067 maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a maxim product. no circu it patent licenses are implied. maxim reserves the right to change the circuitry and specifications without notice at any time. 13 ____________________maxim integrated products, 120 san gabriel drive, sunnyvale, ca 94086 408-737-7600 ? 2008 maxim integrated products is a registered trademark of maxim integrated products, inc. 8lumaxd.eps package outline, 8l umax/usop 1 1 21-0036 j rev. document control no. approval proprietary information title: max 0.043 0.006 0.014 0.120 0.120 0.198 0.026 0.007 0.037 0.0207 bsc 0.0256 bsc a2 a1 c e b a l front view side view e h 0.60.1 0.60.1 ?0.500.1 1 top view d 8 a2 0.030 bottom view 1 6 s b l h e d e c 0 0.010 0.116 0.116 0.188 0.016 0.005 8 4x s inches - a1 a min 0.002 0.95 0.75 0.5250 bsc 0.25 0.36 2.95 3.05 2.95 3.05 4.78 0.41 0.65 bsc 5.03 0.66 6 0 0.13 0.18 max min millimeters - 1.10 0.05 0.15 dim package information (the package drawing(s) in this data sheet may not reflect the most current specifications. for the latest package outline info rmation, go to www.maxim-ic.com/packages .)

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